Switching circuit

ABSTRACT

A method for controlling a switch based on transistors is disclosed. A switching circuit for switching a signal from an input port to an output port thereof is provided. A shunting circuit for switchably shunting the signal from the input port to ground is also provided. A control signal is generated for biasing a control port of the shunting circuit and an approximately complimentary control signal is generated for biasing of the switching circuit to either shunt a signal received at the input port or to switch the signal to the output port. A further bias signal for biasing a port within the switching circuit along the signal path between the input port and the output port is also provided.

INCORPORATION BY REFERENCE TO ANY PRIORITY APPLICATIONS

Any and all applications for which a foreign or domestic priority claimis identified in the Application Data Sheet as filed with the presentapplication are hereby incorporated by reference under 37 CFR 1.57.

FIELD OF THE INVENTION

The invention relates to microwave integrated circuits, and moreparticularly to an enhancement of microwave switch circuits.

BACKGROUND

In recent years, the use of wireless and RF technology has increaseddramatically. The number of cellular telephone subscribers aloneworldwide is expected to reach 3 billion by the end of 2008 according tothe International Telecommunication Union (ITU). Similarly the devicesincorporating wireless technology have expanded, and continue to so. Itis anticipated that the overall market for other wireless devices willexceed cellular telephone units as consumers procure multiple devicesper household.

Wireless devices interface to wireless infrastructures that supportdata, voice and other services via one or more standards. Some examplesof wireless standards in significant deployment today include:

-   -   WiFi [ANSI/IEEE Standard 802.11];    -   WiMAX [IEEE Standard 802.16];    -   Bluetooth [IEEE Standard 802.15.1];    -   Industrial, Scientific and Medical (ISM) [International        Telecommunications Union Recommendations 5.138, 5.150, and        5.280]; and    -   GSM 850/9001180011900 [European Telecommunications Standards        Institute (ETSI)] and its extensions General Packet Radio        Service (GPRS) and Enhanced Datarates for GSM Evolution (EDGE).

Pricing of finished products is often a major factor in the commercialsuccess of products. Accordingly, monolithic integration of theelectronics to result in devices with low parts count—a small number ofintegrated circuits (ICs)—is common practice. In fact, a typical RFsystem will comprise a baseband controller IC, a radio receiver andtransmitter, and an RF signal front-end that may include poweramplifiers, low-noise amplifiers, switches, and filters amongst otherpossible signal conditioning blocks. These integrated circuits aremanufactured using a silicon-based technology platform for basebandelements of the circuit that are ‘logic’ intensive and, typically fromsilicon germanium, gallium arsenide, and indium phosphide for many RFcircuit elements that condition the incoming or outgoing radio signalprimarily in the analog or RF domain. The RF circuit elements form amicrowave circuit path from the RF signal mixers that are up convertingor downconverting the RF signals via amplifiers, microwave filters,circulators, etc. The RF signal is, of course, received from ortransmitted to an RF antenna or other load such as a co-axial cable. AnRF antenna or cable is an RF load for the transmitting circuit or RFsignal front-end. Moreover, a collection of RF circuit elements might bemanifested in the form of a monolithic microwave integrated circuit(MMIC) and may be part of the RF front-end in the form of a module.

Within many wireless consumer electronics products that are intended toreceive or transmit information is a transmit/receive switch circuitthat selectively connects a microwave transmission circuit to the RFload of the consumer electronics product and a microwave receivercircuit to the antenna or cable, such a switch circuit being a SinglePole Double Throw (SPDT) switch. The microwave transmission circuit andmicrowave receiver circuit are often a single bidirectionaltransmit/receive circuit. In other instances where the wireless consumerelectronic product operates with multiple wireless standards there maybe a separate microwave transmission circuit and microwave receivercircuit for each of the wireless standards supported. For example awireless device supporting two wireless standards requiring differentMMIC technologies for each, such as IEEE 802.11a at 5 GHz and IEEE802.16 at 2.4 GHz, would have a Single Pole Quadruple Throw (SPQT)wherein a single common antenna or cable port is selectively coupled toone of two possible transmitter connections and a corresponding one oftwo receiver connections.

Conventionally, high-performance RF/microwave switches are implementedwith depletion-mode GaAs MESFETs or PHEMTs. These devices are chosenbecause they offer very low R_(on) and C_(off) per unit gate width;these parameters determine switch insertion loss and isolation. Thetransistor is turned on by biasing Vgs>Vp, where Vp is the pinchoffvoltage and Vp<0 for a depletion-mode device. The transistor is turnedoff by biasing Vgs<Vp, where a typical value of Vp might be −1.0 V. SoVgs_(on) might be 0 V and Vgs_(off) might be −2 V. This is accomplished,for example, by biasing the source and drain at 2 V and switching thegate to 0 V (off) or 2 V (on).

The D-mode GaAs FET or PHEMT has three major disadvantages for use as ahigh-performance switch. First is the tendency of gate current to flowwhen Vgs>0; the gate forms a Schottky diode to the channel which canturn on for large signal levels or inappropriate bias. Gate current flowleads to sharply increased loss and distortion in the switch. A seconddisadvantage is the absence of a complementary device type (p-channelFET); without a PFET, logic functions consume more power and die area.In some circuits it is difficult to control the switch using standardlow-voltage CMOS levels. A third disadvantage is resulting higher diecost per unit area, which is aggravated by the relatively primitive andarea-intensive ESD protection structures available in most GaAs FETprocesses.

Silicon-based RF/microwave switches that use the CMOS device as the coreswitch element are attractive because of the integration potential ofcombining both logic and RF functionality. In addition, the relativelylow cost when compared to GaAs-based devices makes such Silicon-basedRF/microwave switches attractive for the consumer electronics market.The conventional biasing arrangement and topology of an RF/microwaveswitch is, however, similar when the switch is manufactured using aSilicon-based CMOS technology or GaAs.

It is therefore a goal of the invention to overcome at least some of thelimitations of the prior art.

SUMMARY OF THE INVENTION

In accordance with the invention there is provided a circuit comprising:a first RF switch operable in a first mode and in a second other mode,the RF switch comprising: an input port for receiving an RF signal, anoutput port for in the first mode providing the RF signal and in thesecond other mode other than providing the RF signal, a shunt switch forin the second other mode shunting the RF signal to ground and in thefirst mode for other than shunting the RF signal to ground, and a switchfor in the first mode conducting the RF signal between the input portand the output port and in the second other mode other than conductingthe RF signal between the input port and the output port; and acontroller comprising a switching circuit for providing simultaneously aplurality of control signals comprising: a first signal for biasing theswitch between the first mode and the second other mode; anapproximately complimentary signal for biasing the shunt switch betweenthe second other mode and the first mode; and a biasing signal forbiasing one of a source and a drain of the switch approximately inaccordance with the approximately complimentary signal.

In accordance with another embodiment of the invention there is provideda method comprising: providing a switching circuit for switching asignal from an input port to an output port thereof; providing ashunting circuit for switchably shunting the signal from the input portto ground; providing a control signal for biasing a control port of theshunting circuit and an approximately complimentary control signal forbiasing of a control port of the switching circuit to either shunt asignal received at the input port or to switch the signal to the outputport; and, providing a bias signal for biasing a port within theswitching circuit along the signal path between the input port and theoutput port.

BRIEF DESCRIPTION OF THE DRAWINGS

Exemplary embodiments of the invention will now be described inconjunction with the following drawings, in which:

FIG. 1A illustrates a simple prior art microwave switch circuitaccording to Bergener et al.

FIG. 1B illustrates a typical prior art microwave switch circuitaccording to Bergener et al.

FIG. 2 illustrates a prior art microwave switch according to Burghartz.

FIG. 3A illustrates an exemplary embodiment of the invention forapplying full ON/OFF drive to the RF FETs.

FIG. 3B illustrates a typical performance of the design of FIG. 3A.

FIG. 4 illustrates an exemplary embodiment of the invention applyingdrain-source resistors to the series FETs of FIG. 3A.

FIG. 5 illustrates an exemplary embodiment of the invention wherein theseries FETs of the microwave switch are modified to include inter-gateelectrodes.

DETAILED DESCRIPTION

Referring to FIG. 1A there is shown a simple prior art microwave switchcircuit 100 according to Bergener et al (U.S. Pat. No. 6,804,502). Themicrowave switch circuit 100 comprises four MOSFET transistors 123, 124,127 and 128. The transistors 123 and 124 act as “pass” or “switching”transistors, and are configured to couple respective RF input nodes RF 1Input 121 and RF2 Input 122 to a common RF node RF Common 125. Forexample, when enabled—switched “on,” the switching transistor 123couples a first RF signal applied to RF node RF1 Input port 121 to theRF common node RF Common 125. Similarly, when enabled, the switchingtransistor 124 couples a second RF signal applied to second RF node RF2Input port 122, to the RF common node RF Common 125. The shuntingtransistors, 127 and 128, when enabled, act to shunt the respective RFsignals to ground when their associated RF nodes are uncoupled from theRF common node RF Common 125. This uncoupling occurs when the respectiveswitching transistor, switching transistor 123 or switching transistor124, is electrically connected to the associated node RF1 Input 121 orRF2 Input 122 is turned “off.”

Such a microwave switch circuit 100 when implemented using bulk siliconCMOS RF switches disadvantageously exhibits high insertion loss, lowcompression, and poor linearity performance characteristics. Incontrast, implementing microwave switch circuit 100 with galliumarsenide (GaAs) semiconductor technology overcomes this as thesemi-insulating GaAs substrate material results in parasitic substrateresistances being greatly reduced, thereby reducing RF switch insertionloss. Similarly, the semi-insulating GaAs substrate improves switchisolation. GaAs whilst offering improved performance compared with SiCMOS disadvantageously has higher manufacturing costs. As such it wouldbe beneficial to enhance the performance of Si CMOS RF microwaveswitches. Referring to FIG. 1B illustrated is a prior art microwaveswitch circuit 150 according to Bergener et al that attempts to redressthe performance issues of Si CMOS.

The microwave switch circuit 150 comprises four clusters or “groupings”of MOSFET transistors, identified in FIG. 1B as transistor groupings133, 134, 137 and 138. Two transistor groupings comprise “pass” or“switching” transistor groupings 133 and 134, and two transistorgroupings comprise shunting transistor groupings 137 and 138. Eachtransistor grouping comprises three MOSFET transistors arranged in aserial configuration. For example, in the embodiment shown in FIG. 1B,the switching grouping 133 includes three switching transistors, M133A,M133B, and M133C. Similarly, the switching grouping 134 includes threeswitching transistors, M134A, M134B, and M134C. The shunting grouping137 includes three transistors M137A, M137B, and M137C. Similarly, theshunting grouping 138 includes three transistors, M138A, M138B, andM138C.

As shown in FIG. 1B, microwave switch circuit 150 is controlled by twocontrol signals, SW, and its inverse, SW−. These control signals arecoupled to the gates of their respective transistors through gateresistors. For example, the control signal SW controls the operation ofthe three transistors in the switching transistor grouping 133, M133A,M133B, and M133C, through gate resistors, R133A, R133B, and R133C,respectively. The control signal SW propagates to the switchingtransistor grouping 133 via input node 133A, and is also provided toinput node 138A to control the shunting transistor grouping 138.Similarly, the inverse of SW, SW−, controls the switching transistorgrouping 134 via input node 134. SW− is also provided to input node 137Ato control the shunting transistor grouping 137. SW− is similarlyapplied to the transistors M134A, M134B, and M134C of switchingtransistor grouping 134 via three gate resistors, R134A, R134B, andR134C, respectively.

The switching transistor groupings 133 and 134 act as pass or switchingtransistors, and are configured to alternatively couple RF nodes, RF1Input port 131 and RF2 Input port 132, to a common RF node RF Common135. For example, when enabled, the switching transistor grouping 133couples an RF signal applied to RF input node RF1 Input port 131 to theRF common node RF Common 135. Similarly, when enabled, the switchingtransistor grouping 134 couples a RF signal from the RF node RF2 Inputport 132 to the RF common node RF Common 135. The shunting transistorgroupings, 137 and 138, when enabled, act to shunt signals from the RFinput nodes to ground when their associated RF nodes are uncoupled fromthe RF common node, i.e., when the switching transistor grouping, 133 or134, that is electrically connected to the associated input node isturned “off.”

As taught by Bergener the microwave switch circuit 150 is notmanufactured using a conventional Si CMOS manufacturing methodology.Rather the MOSFET transistors within the transistors groupings 133, 134,137 and 138 are implemented using a fully insulating substratesilicon-on-insulator (SOI) technology. More specifically, Bergenerteaches using “Ultra-Thin-Silicon” (UTSi), which is also known asUltrathin Silicon-on-Sapphire due to the use of thin film silicon on asapphire substrate rather than a silicon wafer. The fully insulatingsapphire substrate enhances the performance characteristics of the RFswitch by reducing the deleterious substrate coupling effects associatedwith non-insulating and partially insulating substrates. For example,improvements in insertion loss are realized by lowering the transistor“on” resistances and by reducing parasitic substrate resistances. Inaddition, switch isolation is improved using the fully insulatingsubstrates provided by UTSi technology. Owing to the fully insulatingnature of silicon-on-sapphire technology, the parasitic capacitancebetween the nodes of the microwave switch circuit 150 is greatly reducedas compared with bulk CMOS and other traditional integrated circuitmanufacturing technologies.

However, whilst Bergener teaches a CMOS circuit, it is still onemanufactured using unconventional manufacturing technology differentfrom the bulk of low cost Si CMOS, which employs a low resistivitysilicon substrate. An alternative approach is shown in respect of FIG.2, which illustrates a prior art microwave switch 200 according toBurghartz. The microwave switch 200 as shown is an SPST switch thatincludes a port, RF input port 221, where an RF signal is applied to themicrowave switch 200, an output port, RF Output port 222, and a switchcontrol port 223 which receives a bias signal for controlling an ON andOFF status of the switch. The RF signal appears at output port 222 withlow insertion loss in the ON state, and with high insertion loss in theOFF state.

First FET 201 is electrically connected to both the RF Input port 221and RF Output port 222 and includes gate 201G, source 201S, drain 201D,and back gate contact 201B. First FET 201 as well as the other FETs 202,203, and 204 are silicon MOSFETs operating in depletion mode. Gate 201Gof first FET 201 is electrically connected to switch control port 223,the source 201S to the RF input port 221, and the drain 201D to the RFoutput port 222. The back gate contact 201B is coupled to source 203Sand drain 204D of second and third FETs 202 and 203. Drain 202D ofsecond FET 202 is electrically connected to RF Input port 221, while thesource 203S of third FET is electrically connected to ground potential.The respective back gate contacts 202B and 203B of the second and thirdFETs 202 and 203 are commonly electrically connected to ground.

The gate 202G of second FET 202 is electrically connected to switchcontrol port 223, while gate 203G of third FET 203 is electricallyconnected to the output port of inverter 218. The input signal port ofthe inverter 218 is electrically connected to switch control port 223.The output port of the inverter 218 is electrically connected to thegate 204G of the fourth FET 204, the shunt FET, which has its source204S and back gate 204B at ground and its drain 204D coupled to RFoutput 222. In the ON-state of the microwave switch 200, a bias controlsignal applied to switch control port 223 is in a first state, e.g.,VGS=0V, thereby turning first and second FETs 201 and 2020N. Also, thirdand fourth FETs 203 and 204 are each OFF, since inverter 118 providesbias of opposite state to the gates 203G and 204G of third and fourthFETs 203 and 204, respectively. With second FET 2020N, the back gate201B and source 201S of the first FET 201 are electrically connectedtogether through the second FET 202. This electrical connection ofsource 201S and back gate 201B regions minimizes the on-resistance offirst FET 201. Also, in the ON state, third FET 203 is off and thuspresents high shunt impedance, which limits additional loss for themicrowave switch 200. In the OFF state of the microwave switch 200, thebias control signal applied to switch control port 223 is in theopposite state, and hence first and second FETs 201 and 202 are OFFwhile third and fourth FETs 203 and 204 are ON. As a result, back gatecontact 201B is connected via third FET 203 to ground potential, assource 203S is at ground potential. This maximizes the off-resistance ofthe series FET, first FET 201. Also fourth FET 204 is ON, whichincreases the isolation, insertion loss, of the overall microwave switch200 in the OFF state, since an RF short to ground is provided forcoupling most of the power that leaks through first FET 201 to groundand not the RF output port 222.

Insertion loss within a microwave switch such as prior art switch 200 isleast when the FETs within the switching group, i.e. first FET 201, aredriven to their hardest ON state. Similarly highest isolation occurswhen the FETs within the switching group are driven to their hardest OFFstate and the shunt group, i.e. fourth FET 204, are driven to theirhardest ON state. An exemplary embodiment of the invention for applyingON/OFF drive to the switching and shunt FETs is shown by microwaveswitch circuit 300. As shown an antenna 355 is intended for connectionto one of three circuits, namely Tx circuit 385, Rx circuit 365, andtest circuit 375. Disposed between each of these three circuits and theantenna 355 are switching circuits 310, 360 and 370, respectively.

Considering the first switching circuit 310, which is often typical ofall three switching circuits 310, 360 and 370, then the switching pathbetween the antenna 355 and Tx circuit 385 comprises first decouplingcapacitor 321, first through third switching FETs 331 through 333, andsecond decoupling capacitor 324. The first through third switching FETs331, 332, and 333 are cascaded drain to source, and for each their gatecontact is electrically coupled to a second output port 350B of a switchcontroller 350 via resistors 312, 313, and 314, respectively. The drainof the FET 331 is also electrically coupled via a resistor 311 to afirst output port 350A of the switch controller 350. The third switchingFET 333 has its source capacitively coupled via capacitor 315 to thedrain contact of upper FET 341 of shunt transistor grouping comprisingupper FET 341, middle FET 342, and lower FET 343. As with the switchingtransistor grouping, the shunt transistor grouping of FETs 341, 342, and343 are electrically coupled source contact to drain contact, whilst thesource contact of lower FET 343 is capacitively coupled to ground andresistively coupled to port 350B via resistor 391. The gate contacts ofupper FET 341, middle FET 342, and lower FET 343 are all electricallycoupled to a third output port 350C of the switch controller 350 viaresistors 316, 317, and 318, respectively.

The switch controller 350 is controlled from an input port Switch Tx(SWTx) 310A. Also electrically coupled to the switch controller 350 arelower voltage rail V_(LO) at lower voltage port 310C and upper voltagerail V_(HI) at upper voltage port 310B. V_(HI) is provided from aregulator 380 to which upper voltage port 310B is electrically connectedvia regulator output port 380B. The other regulator output ports 380Cand 380D are interconnected to equivalent upper voltage ports within theswitching circuits 360 and 370, respectively. Switching circuit 360 isinterfaced to the antenna 355 and Rx circuit 365 is controlled viaSwitch Rx (SWRx) port 360A. Similarly switching circuit 370 disposedbetween the antenna 355 and test circuit 375 is controlled via Switch(SWBT) port 370A. The regulator 380 is provided with a voltage to beregulated from regulator input port 380A, for example from a battery ofa wireless handheld device V_(BAT).

SWTx 310A is electrically coupled to the gates of first and secondcontroller transistors 351 and 353. The drain of first controllertransistor 351 is electrically coupled to the upper voltage rail V_(HI),the source of first controller transistor 351 is electrically coupled tothe drain of second controller transistor 353, and the drain of secondcontroller transistor 353 is electrically coupled to the lower voltagerail V_(LO). Similarly third and fourth controller transistors 352 and354, respectively, are disposed between the upper voltage rail V_(HI)and lower voltage rail V_(LO). The gates of the third and fourthcontroller transistors are electrically coupled to the mid-pointdrain-source connection between the first and second controllertransistors 351 and 353, respectively. First controller output port 350Ais also electrically coupled to this mid-point drain-source connection,as is the third controller output port 350C. The second controlleroutput port 350B is electrically coupled to the mid-point drain-sourceconnection between the third and fourth controller transistors 352 and354, respectively.

Accordingly in operation, if a SWTx low signal is applied to SWTx port310A this results in the switching FETs 331, 332, and 333 being turnedoff with source-drain voltage at V_(HI), from first controller outputport 350A, and the gates at V_(LO) or ground from second controlleroutput port 350B. In this state, the shunt FETs 341, 342, and 343 areturned on with gate-voltage at V_(HI) from third controller output port350C, and the source-drain voltage at V_(LO) or ground from secondcontroller output port 350B. If SWTx is high, V_(HI), then the switchingFETs are turned on with the source-drain voltage at V_(LO) and the gatesbiased at V_(HI); the shunt FETs are turned off with gates—at V_(LO) orground and the source-drain voltage at V_(HI).

As shown in FIG. 3, the drain of a last shunt FET 343 at a fourthcontroller output port 350D is coupled to a signal complementary to thatprovided to the gate thereof. Here, the complementary signal is a signalprovided to the gates of the switching FETs 331, 332, and 333. Thisprovides a similar advantage for the shunt FET switching as is providedand explained for the switching FET.

Advantageously, each switching circuit, such as first switching circuit310, provides approximately maximum possible “on” and “off” drivevoltages to the FETs in switching and shunt paths. Additionally ACcoupling of the switching circuit with respect of the antenna 355 andelectrically coupled circuit, i.e. Tx circuit 385, is inherentlyprovided. Optionally the capacitors 321 and 324 are chosen to beresonant with the bond wires interconnecting the switch circuit 300,comprising switching circuit 310, 360 and 370, to the antenna 355, Txcircuit 385, Rx circuit 365, and test circuit 375. For example, for aswitch circuit designed to operate at 2.45 GHz where a typical bond wireinductance is 500 pH then these capacitors would be specified at nominal8.4 pF.

As described supra in respect of microwave switch circuit 300 theregulator 380 provides a regulated output voltage V_(HI) to theregulator output ports 380B, 380C, and 380D which are electricallycoupled to the switching circuits 310, 360, and 370, respectively.Optionally, regulator 380 is also interfaced to circuitry thatdetermines whether a switching circuit has been enabled, i.e. has one ofSWTx, SWRx, and SWBT been set to enable a respective switching circuit.If none of these three control signals has been enabled, this obviatesregulation of voltage such that V_(HI) generated is directly suppliedwithout regulation and the control logic operates with the circuitworking at the same voltage levels, namely ground or V_(LO) and V_(HI),so as to ensure no latch-up within the circuit and unwanted powerdissipation. Since no average current is drawn from V_(HI) it merelyserves as a power supply for static CMOS inverters within the controllercircuits such as controller circuit 350.

Referring to FIG. 3B illustrated is a typical performance according tothe design of FIG. 3A. As shown, there is first time-voltage graph 350Adepicting voltage at each drain contact within the switching FETs 331,332, and 333. Hence there is shown first curve 350AI representing drainvoltage Vd1 from first switching FET 331, second curve 350A2representing drain voltage Vd2 from the second switching FET 332, andthird curve 350A3 representing drain voltage Vd3 from the thirdswitching FET 333. The voltage appearing at each drain voltage isreduced from first switching curve 350A1, a swing of approximately 26V,to third switching curve 350A3, with a swing of approximately 5V.

Referring to FIG. 4 there is illustrated an exemplary embodiment of theinvention wherein drain-source resistors are provided to the switchingFETs 331, 332 and 333 of FIG. 3A. As shown in microwave switch circuit400, a single switching circuit 410 is depicted between antenna 355 andTx circuit 385 and is controlled from SWTx port 310A. The singleswitching circuit 410 now has resistors 411, 412, and 413 disposedbetween the drain and source contacts of each of switching FETs 331, 332and 333, respectively. Properly selected resistors act to reduceharmonic distortion.

Referring to FIG. 5 there is illustrated an exemplary embodiment of theinvention wherein the switching FETs of the microwave switch aremodified to include inter-gate electrodes. As shown microwave switchcircuit 500 comprises a switching circuit 510 disposed between antenna355 and Tx circuit 385. Now each of the switching FETs 531 through 533is implemented as shown by FET structure 550. As such, the FET structure550 comprises source contact 550S, drain contact 550D, and gate contacts550G1 and 550G2. However, now disposed between the gate contacts 550G1and 550G2 is intergate contact 5501G.

Accordingly, resistors between the drain-source of the switching FETs,such as resistors 411, 412, and 413 of FIG. 4, are replaced by pairs ofresistors. Hence first switching FET 531 has first resistor 541A betweendrain and intergate electrode and second resistor 541B between theintergate electrode and source. Second switching FET 532 has third andfourth resistors 542A and 542B disposed to connect the integrate contact550G to the drain and source contacts, and third switching FET 533 hasfifth and sixth resistors 543A and 543B disposed to connect theintergate contact 550G to the drain and source contacts. Whilst eachswitching FET 531 through 533 is depicted with a single resistor 312through 314 between the gate contacts and the switch control circuit,each gate contact 550G 1 and 550G2 optionally is electrically coupledvia a separate resistor (not shown for clarity). Biasing the intergateelectrode changes the pinch-off voltage, thereby improving suppressionof harmonics further within the switching FETs.

Optionally the switching FET configurations of FIGS. 4 and 5 are appliedto the shunt FETs even though harmonic suppression whilst shunting RFpower to ground is not typically as important as it is within theswitching path. The embodiments herein described are applicable tosilicon CMOS based FETs thereby allowing for low cost manufacturing aswell as offering integration of the switching circuits with standard SiCMOS transmit/receive circuits.

Numerous other embodiments may be envisaged without departing from thespirit or scope of the invention.

What is claimed is:
 1. A radio frequency (RF) device comprising: atransmit circuit configured to provide an RF signal including transmitinformation; an antenna configured to transmit the RF signal; and amicrowave switch configured to provide a switching path between theantenna and the transmit circuit and including at least one switchingFET configured to conduct the RF signal between the transmit circuit andthe antenna in a first mode of operation, at least one shunt FETconfigured to shunt the RF signal to ground in a second mode ofoperation, and a plurality of control switches configured to turn on theat least one shunt FET in the second mode and to turn off the at leastone shunt FET in the first mode, to turn off the at least one switchingFET in the second mode and to turn on the at least one switching FET inthe first mode, to increase a voltage difference between the gate andthe drain of the at least one switching FET, and to increase a voltagedifference between the gate and the drain of the at least one shunt FET.2. The RF device of claim 1 wherein the control switches are configuredto provide a first control signal to turn on the at least on switchingFET in the first mode, to turn off the at least one switching FET in thesecond mode, and to increase a voltage difference between the gate andthe drain of the at least one shunt FET.
 3. The RF device of claim 2wherein the control switches are further figured to provide a secondcontrol signal to turn on the at least one shunt FET in the second mode,to turn off the at least one shunt FET in the first mode, and toincrease a voltage difference between the gate and the drain of the atleast one switching FET.
 4. The RF device of claim 3 wherein the firstand second control signals being approximately complementary signals. 5.The RF device of claim 2 wherein the first control signal drives a gateof the switching FET and biases one of a drain and a source of the shuntFET.
 6. The RF device of claim 1 wherein the second control signaldrives a gate of the shunt FET and biases one of a drain and a source ofswitching FET.
 7. The RF device of claim 1 wherein the at least oneswitching FET includes a resistor disposed between a source contact ofthe switching FET and a drain contact of the switching FET to reduceharmonic distortion.
 8. The RF device of claim 1 wherein the at leastone switching FET includes an intergate electrode disposed between apair of switching FET gate contacts for biasing an integrate region toadjust a characteristic of the switching FET, a first feed-forwardresistor electrically coupled to a drain contact of the switching FETand the intergate electrode, and a second feed-forward resistor coupledto a source contact of the switching FET and the integrate electrode. 9.The RF device of claim 1 wherein the microwave switch further includes afirst decoupling capacitor disposed along the switching path between theantenna and the at least one switching FET and a second decouplingcapacitor disposed along the switching path between the transmit circuitand the at least one switching FET, the values of the first and seconddecoupling capacitors chosen to resonate with bond wires interconnectingthe microwave switch.
 10. A radio frequency (RF) device comprising: anantenna configured to receive a RF signal including receive information;a receive circuit configured to process the RF signal and extract thereceive information; and a receive microwave switch configured toprovide a receive switching path between the antenna and the receivecircuit and including at least one switching FET configured to conductthe RF signal between the antenna and the receive circuit in a firstmode of operation, at least one shunt FET configured to shunt the RFsignal to ground in a second mode of operation, and a controller circuitconfigured to provide control signals including a first control signalfor driving the at least one switching FET between the first mode andthe second mode, a second control signal for driving the at least oneshunt FET between the second mode and the first mode, a first biasingsignal for biasing one of a source and a drain of the at least oneswitching FET, and a second biasing signal for biasing one of a sourceand a drain of the at least one shunt FET.
 11. The RF device of claim 10wherein the second control signal is approximately complementary to thefirst control signal.
 12. The RF device of claim 10 wherein the firstbiasing signal is approximately in accordance with the second controlsignal.
 13. The RF device of claim 10 wherein the second biasing signalis approximately in accordance with the first control signal.
 14. The RFdevice of claim 10 further comprising a transmit circuit configured toprovide an RF signal including transmit information and a transmitmicrowave switch configured to provide a transmit switching path betweenthe antenna and the transmit circuit.
 15. A method of operating a radiofrequency (RF) device, the method comprising: receiving an RF signal ata first port; conducting the RF signal between the first port and asecond port through at least one switching FET in a first mode ofoperation and shunting the RF signal through at least one shunt FET toground in a second mode of operation, operating in the first modeincluding driving a gate of the at least one shunt FET to turn off theat least one shunt FET, driving a gate of at least one switching FET toturn on the at least one switching FET, and biasing one of a source anda drain of the at least one switching FET to increase a voltagedifference between the gate and the drain of the at least one switchingFET, operating in the second mode including driving a gate of at leastone shunt FET to turn on the at least one shunt FET, driving a gate ofat least one switching FET to turn off the at least one switching FET,and biasing a one of a source and a drain of the at least one shunt FETto increase a voltage different between the gate and the drain of the atleast one shunt FET; and processing the RF signal at the second portwhen operating in the first mode.
 16. The method of claim 15 furthercomprising receiving a switch control signal.
 17. The method of claim 16further comprising generating a first control signal to turn on the atleast on switching FET in the first mode and to turn off the at leastone switching FET in the second mode, the first control signal based atleast in part on the switch control signal.
 18. The method of claim 17further comprising generating a second control signal to turn on the atleast one shunt FET in the second mode and to turn off the at least oneshunt FET in the first mode, the first and second control signals beingapproximately complementary signals.
 19. The method of claim 18 furthercomprising generating a first bias signal to increase the voltagedifference between the gate and the drain of the at least one switchingFET, the first bias signal and the first control signal beingapproximately complementary signals.
 20. The method of claim 19 furthercomprising generating a second bias signal to increase the voltagedifference between the gate and the drain of the at least one shunt FET,the second bias signal and the second control signal being approximatelycomplementary signals.